Description
Dataset for publishable figures in a "On-Chip Frequency Conversion Using Kinetic Inductance Within a Coplanar Waveguide" manuscript to be submitted to IEEE Transactions on Applied Superconductivity. This work presents a method of frequency conversion which exploits the kinetic inductance of a superconducting coplanar waveguide. Both frequency doubling and tripling are examined, with attention paid to conversion efficiency. This approach allows up-conversion to be implemented in a cryogenic environment, which can simplify the design of cryogenic systems. We achieved a conversion efficiency of 12.7% when up-converting a 10 GHz fundamental tone to the 20 GHz second harmonic, which is an improvement compared to higher-power room-temperature commercial offerings. To better understand device behavior, we also develop a measurement-based model using a harmonic balance simulation, and achieved good agreement between measurements and simulations.
Resources
| Name | Format | Description | Link |
|---|---|---|---|
| README.txt | Text | READ ME file | Open resource |
| TAS24A_Fig1.fig | Unknown | Data used in Figure 1 of [1]. Harmonics are measured with a VNA by offsetting the frequency provided by the signal generator and the measurement frequency of the VNA. We plot example second and third harmonic generation data as a function of dc bias current using a fundamental tone at 9.87 GHz. See [1] for additional information. | Open resource |
| TAS24A_Fig1.txt | Unknown | Data used in Figure 1 of [1]. Harmonics are measured with a VNA by offsetting the frequency provided by the signal generator and the measurement frequency of the VNA. We plot example second and third harmonic generation data as a function of dc bias current using a fundamental tone at 9.87 GHz. See [1] for additional information. | Open resource |
| TAS24A_fig3.fig | Unknown | Data used in Figure 3 of [1]. We show the measured results for the distributed capacitance and inductance of the coplanar waveguide, plotted versus dc current (x-axis) as the fractional change (y-axis) from the zero-current values of 132.2 pF/m and 999.6 nH/m. See [1] for additional information. | Open resource |
| TAS24A_Fig3.txt | Unknown | Data used in Figure 3 of [1]. We show the measured results for the distributed capacitance and inductance of the coplanar waveguide, plotted versus dc current (x-axis) as the fractional change (y-axis) from the zero-current values of 132.2 pF/m and 999.6 nH/m. See [1] for additional information. | Open resource |
| TAS24A_Fig4a.fig | Unknown | Data used in Figure 4 of [1]. Time domain reflectometry (TDR) measurements of the system showing system characteristic impedance versus time/distance (a) are used to determine changes in the electrical length of the chip as a function of dc bias current based on a sharp feature at the transition off of the chip (b). This change is a direct, independent measurement of the quadratic nonlinearity coefficient of the inductance (c). See [1] for additional information. | Open resource |
| TAS24A_Fig4a.txt | Unknown | Data used in Figure 4 of [1]. Time domain reflectometry (TDR) measurements of the system showing system characteristic impedance versus time/distance (a) are used to determine changes in the electrical length of the chip as a function of dc bias current based on a sharp feature at the transition off of the chip (b). This change is a direct, independent measurement of the quadratic nonlinearity coefficient of the inductance (c). See [1] for additional information. | Open resource |
| TAS24A_Fig4b.fig | Unknown | Data used in Figure 4 of [1]. Time domain reflectometry (TDR) measurements of the system showing system characteristic impedance versus time/distance (a) are used to determine changes in the electrical length of the chip as a function of dc bias current based on a sharp feature at the transition off of the chip (b). This change is a direct, independent measurement of the quadratic nonlinearity coefficient of the inductance (c). See [1] for additional information. | Open resource |
| TAS24A_Fig4b.txt | Unknown | Data used in Figure 4 of [1]. Time domain reflectometry (TDR) measurements of the system showing system characteristic impedance versus time/distance (a) are used to determine changes in the electrical length of the chip as a function of dc bias current based on a sharp feature at the transition off of the chip (b). This change is a direct, independent measurement of the quadratic nonlinearity coefficient of the inductance (c). See [1] for additional information. | Open resource |
| TAS24A_Fig4c.fig | Unknown | Data used in Figure 4 of [1]. Time domain reflectometry (TDR) measurements of the system showing system characteristic impedance versus time/distance (a) are used to determine changes in the electrical length of the chip as a function of dc bias current based on a sharp feature at the transition off of the chip (b). This change is a direct, independent measurement of the quadratic nonlinearity coefficient of the inductance (c). See [1] for additional information. | Open resource |
| TAS24A_Fig4c.txt | Unknown | Data used in Figure 4 of [1]. Time domain reflectometry (TDR) measurements of the system showing system characteristic impedance versus time/distance (a) are used to determine changes in the electrical length of the chip as a function of dc bias current based on a sharp feature at the transition off of the chip (b). This change is a direct, independent measurement of the quadratic nonlinearity coefficient of the inductance (c). See [1] for additional information. | Open resource |
| TAS24A_Fig5a.txt | Unknown | Data and simulated data used in Figure 5 of [1]. We plot (a) a comparison between the measured transmission S21 through the CPW and the result of an ADS harmonic balance simulation. The model uses 105 lumped-element stages; all model parameters are determined from measurements. (b) Measured and simulated change in phase of a tone at 10 GHz as a function of dc current bias. See [1] for additional information. | Open resource |
| TAS24A_Fig5b.txt | Unknown | Data and simulated data used in Figure 5 of [1]. We plot (a) a comparison between the measured transmission S21 through the CPW and the result of an ADS harmonic balance simulation. The model uses 105 lumped-element stages; all model parameters are determined from measurements. (b) Measured and simulated change in phase of a tone at 10 GHz as a function of dc current bias. See [1] for additional information. | Open resource |
| TAS24A_Fig5.fig | Unknown | Data and simulated data used in Figure 5 of [1]. We plot (a) a comparison between the measured transmission S21 through the CPW and the result of an ADS harmonic balance simulation. The model uses 105 lumped-element stages; all model parameters are determined from measurements. (b) Measured and simulated change in phase of a tone at 10 GHz as a function of dc current bias. See [1] for additional information. | Open resource |
| TAS24A_Fig6a.fig | Unknown | Data used in Figure 6 of [1]. We plot the second harmonic (a) and third harmonic (b) conversion efficiency at the optimum dc bias current and fundamental tone RF power plotted versus measurement frequency. The measurement was repeated ten times. The standard deviation of each data point is less than or equal to 0.1% in (a) and 0.01% in (b). See [1] for additional information. | Open resource |
| TAS24A_Fig6a.txt | Unknown | Data used in Figure 6 of [1]. We plot the second harmonic (a) and third harmonic (b) conversion efficiency at the optimum dc bias current and fundamental tone RF power plotted versus measurement frequency. The measurement was repeated ten times. The standard deviation of each data point is less than or equal to 0.1% in (a) and 0.01% in (b). See [1] for additional information. | Open resource |
| TAS24A_Fig6b.fig | Unknown | Data used in Figure 6 of [1]. We plot the second harmonic (a) and third harmonic (b) conversion efficiency at the optimum dc bias current and fundamental tone RF power plotted versus measurement frequency. The measurement was repeated ten times. The standard deviation of each data point is less than or equal to 0.1% in (a) and 0.01% in (b). See [1] for additional information. | Open resource |
| TAS24A_Fig6b.txt | Unknown | Data used in Figure 6 of [1]. We plot the second harmonic (a) and third harmonic (b) conversion efficiency at the optimum dc bias current and fundamental tone RF power plotted versus measurement frequency. The measurement was repeated ten times. The standard deviation of each data point is less than or equal to 0.1% in (a) and 0.01% in (b). See [1] for additional information. | Open resource |
| TAS24A_Fig7a.fig | Unknown | Simulated data used in Figure 7 of [1]. We plot the simulated second harmonic conversion efficiency versus frequency to compare the measured 87 Ω CPW (blue) to a 50 Ω CPW (red) that is better matched to the environment. For the matched CPW, the ripple behavior is eliminated and broadband conversion efficiencies over 10% are expected for second harmonic generation frequencies from 17 GHz to over 40 GHz. See [1] for additional information. | Open resource |
| TAS24A_Fig7a.txt | Unknown | Simulated data used in Figure 7 of [1]. We plot the simulated second harmonic conversion efficiency versus frequency to compare the measured 87 Ω CPW (blue) to a 50 Ω CPW (red) that is better matched to the environment. For the matched CPW, the ripple behavior is eliminated and broadband conversion efficiencies over 10% are expected for second harmonic generation frequencies from 17 GHz to over 40 GHz. See [1] for additional information. | Open resource |
| TAS24A_Fig7b.fig | Unknown | Simulated data used in Figure 7 of [1]. We plot the simulated second harmonic conversion efficiency versus frequency to compare the measured 87 Ω CPW (blue) to a 50 Ω CPW (red) that is better matched to the environment. For the matched CPW, the ripple behavior is eliminated and broadband conversion efficiencies over 10% are expected for second harmonic generation frequencies from 17 GHz to over 40 GHz. See [1] for additional information. | Open resource |
| TAS24A_Fig7b.txt | Unknown | Simulated data used in Figure 7 of [1]. We plot the simulated second harmonic conversion efficiency versus frequency to compare the measured 87 Ω CPW (blue) to a 50 Ω CPW (red) that is better matched to the environment. For the matched CPW, the ripple behavior is eliminated and broadband conversion efficiencies over 10% are expected for second harmonic generation frequencies from 17 GHz to over 40 GHz. See [1] for additional information. | Open resource |
| TAS24A_Fig8.fig | Unknown | Data used in Figure 8 of [1]. We plot the measured reflection S11 data used to calculate the distributed inductance L′ and capacitance C′ based on the minima (red circles) and maxima (green circles) reflectance. See [1] for additional information. | Open resource |
| TAS24A_Fig8.txt | Unknown | Data used in Figure 8 of [1]. We plot the measured reflection S11 data used to calculate the distributed inductance L′ and capacitance C′ based on the minima (red circles) and maxima (green circles) reflectance. See [1] for additional information. | Open resource |